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參數資料
| 型號： | 935269495115 |
| 廠商： | NXP SEMICONDUCTORS |
| 元件分類： | 穩壓器 |
| 英文描述： | 0.3 A SWITCHING REGULATOR, 57.5 kHz SWITCHING FREQ-MAX, PDSO5 |
| 封裝： | 1.50 MM, PLASTIC, MO-178, SOT-25, SOT-23, SOP-5 |
| 文件頁數： | 4/21頁 |
| 文件大小： | 333K |
| 代理商： | 935269495115 |
Philips Semiconductors
Product data
SA57254-XX
CMOS switching regulator (PWM controlled)
2001 Aug 01
12
Determining the value of the boost inductor
The precise value of the boost inductor is not critical to the operation
of the SA57254-XX. The value of the boost inductor should be
calculated to provide continuous-mode operation over most of its
operating range. The converter may enter the discontinuous-mode
when the output load current falls to less than about 20 percent of
the full-load current.
At low input voltages, the time required to store the needed energy
lengthens, but the time needed to empty the inductor’s core of its
energy shrinks. Conversely, at high input voltages, the time needed
to store the energy shrinks while the time needed to empty the core
increases. See Equations (1) and (3). At the extremes of these
conditions, the converter will fall out of regulation, that is the output
voltage will begin to fall, because the time needed for either storing
or emptying the stored inductor energy is too short to support the
output load current.
To determine the nominal value of the inductance, use Equation (4).
L
0 ^
V
IN(min)
Ton
I
peak
Eqn. (4)
Where:
VIN(min) is the lowest expected input operating voltage (V).
Ton is about 10 s or one-half the switching period (s).
Ipeak is the maximum peak current for the SA57254-XX (0.3 A).
This is an estimated inductor value and you can select an
inductance value slightly higher or lower with little effect on the
converter’s operation. If the design falls out of regulation within the
desired operating range, reduce the inductance value, but by no
more than 30 percent.
Determining the minimum value of the capacitors
The input and output capacitors experience the current waveforms
seen in Figures 25 and 26. The peak currents can be typically
between 3 to 6 times the average currents flowing into the input and
from the output. This makes the choice of capacitor an issue of how
much ripple voltage can be tolerated on the capacitor’s terminals
and how much heating the capacitor can tolerate. At the power
levels produced by the SA57254-XX heating is not a major issue.
The Equivalent Series Resistance (ESR) of the capacitor, the
resistance that appears between its terminals, and the actual
capacitance causes heat to be generated within the case whenever
there is current entering or exiting the capacitor. ESR also adds to
the apparent voltage drop across the capacitor. The heat that is
generated can be approximated by Equation (5).
P
D(in watts) ^ (1.8Iav)
2 (R
ESR)
Eqn. (5)
ESR’s effect on the capacitor voltage is given by Equation (6).
DV
C ^ Ipeak(RESR)
Eqn. (6)
(expressed as Vp–p)
A ceramic capacitor would typically be used in this application if the
required value is less than 1 – 10
F, or a tantalum capacitor for
required values of 10
F and above. Lower cost aluminum electrolytic
capacitors can be used, but you should confirm that the higher ESRs
typically exhibited by these capacitors does not cause a problem.
The minimum value of the output capacitor can be estimated by
Equation (7).
C
OUT u
(
I
OUT(max))(Toff)
V
ripple(p
*p)
Eqn. (7)
Where:
IOUT is the average value of the output load current (A).
Toff is the nominal off–time of the power switch (sec) [10 s].
Vripple is the desired amount of ripple voltage (Vp–p).
Finding the value of the input capacitor is done by Equation (8).
C
IN u
(
I
peak)(Ton)
V
drop
Eqn. (8)
Where:
Ipeak is the expected maximum peak current of the switch (A).
Ton is the on-time of the switch (sec) [10 s].
Vdrop is the desired amount of voltage drop across the capacitor
(Vp–p).
These calculations should produce a good estimate of the needed
values of the input and output capacitors to yield the desired ripple
voltages.
Selecting the output rectifier
The output rectifier (D) is critical to the efficiency and low-noise
operation of the boost converter. The majority of the loss within the
supply will be caused by the output rectifier. Three parameters are
important in the rectifier’s operation within a boost-mode supply.
These are defined below.
Forward voltage drop (Vf)—This is the voltage across the rectifier
when a forward current is flowing through the rectifier. A P-N
ultra-fast diode exhibits a 0.7 – 1.4 volt drop, and this drop is
relatively fixed over the range of forward currents. A Schottky diode
exhibits a 0.3 – 0.6 volt drop and appears more resistive during the
forward conduction periods. That is, its forward voltage drop
increases with increasing currents. You can gain an advantage by
purposely over-rating the current rating of a Schottky rectifier to
minimize this increasing voltage drop.
Reverse recovery time (Trr)—This is an issue when the boost
supply is operating in the continuous-mode. Trr is the amount of time
required for the rectifier to assume an open circuit when a forward
current is flowing and a reverse voltage is then placed across its
terminals. P-N ultra-fast rectifiers typically have a 25–40 ns reverse
recovery time. Schottky rectifiers have a very short or no reverse
recovery time.
Forward recovery time (Tfr)—This is the amount of time before a
rectifier begins conducting forward current after a forward voltage is
placed across its terminals. This parameter is not always well
specified by the rectifier manufacturers. It causes a spike to appear
when the power switch turns off. This particular point in its operation
causes the most radiated noise. Several rectifiers may have to be
evaluated for the prototype. After the final output rectifier selection is
made, if the spike is still causing a problem a small passive snubber
can be placed across the rectifier.
For this boost application, the best choice of output rectifier is a low
forward drop, 0.5 – 1 ampere, 20 volt Schottky rectifier such as the
Philips part number BAT120A.
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