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參數資料
| 型號： | ADP3167JR |
| 廠商： | ANALOG DEVICES INC |
| 元件分類： | 穩壓器 |
| 英文描述： | 5-Bit Programmable 2-Phase Synchronous Buck Controller |
| 中文描述： | DUAL SWITCHING CONTROLLER, 2000 kHz SWITCHING FREQ-MAX, PDSO16 |
| 封裝： | SOIC-16 |
| 文件頁數： | 10/16頁 |
| 文件大小： | 292K |
| 代理商： | ADP3167JR |
REV. B
–10–
ADP3160/ADP3167
R
SENSE
The value of R
SENSE
is based on the maximum required output
current. The current comparator of the ADP3160 has a mini-
mum current limit threshold of 142 mV. Note that the 142 mV
value cannot be used for the maximum specified nominal current,
as headroom is needed for ripple current and tolerances.
The current comparator threshold sets the peak of the inductor
current yielding a maximum output current, I
O
, which equals
twice the peak inductor current value less half of the peak-to-
peak inductor ripple current. From this the maximum value of
R
SENSE
is calculated as:
R
V
I
I
mV
+
6 1
A
A
m
SENSE
CS CL
(
MIN
O
2
L RIPPLE
(
2
￡
+
=
=
W
)(
)
)
.
.
.
142
26 7
4 3
(6)
In this case, 4 m
W
was chosen as the closest standard value.
Once R
SENSE
has been chosen, the output current at the point
where current limit is reached, I
OUT(CL)
, can be calculated using
the maximum current sense threshold of 172 mV:
I
V
R
I
mV
m
W
A
A
OUT CL
CS CL
(
MAX
SENSE
L RIPPLE
(
(
)
)(
)
)
–
–
.
.
=
￥
=
￥
=
2
2
172
4
12 2
73 8
(7)
At output voltages below 425 mV, the current sense threshold is
reduced to 95 mV, and the ripple current is negligible. There-
fore, at dead short the output current is reduced to:
I
mV
m
W
A
OUT SC
(
)
.
=
￥
=
2
95
4
47 5
(8)
To safely carry the current under maximum load conditions, the
sense resistor must have a power rating of at least:
P
I
R
R
SENSE RMS
SENSE
SENSE
=
￥
(
)
2
(9)
where:
I
I
n
V
h
V
SENSE RMS
O
OUT
￥
IN
(
)
2
2
=
￥
(10)
In this formula, n is the number of phases, and is the converter
efficiency, in this case assumed to be 85%. Combining Equations 9
and 10 yields:
P
A
V
V
m
mW
R
SENSE
=
￥
￥
W =
53 4
2
1 7
.
0 85 12
.
4
950
2
.
Power MOSFETs
In the standard 2-phase application, two pairs of N-channel
power MOSFETs must be used with the ADP3160 and
ADP3412, one pair as the main (control) switches and the
other pair as the synchronous rectifier switches. The main
selection parameters for the power MOSFETs are V
GS(TH)
and R
DS(ON)
. The minimum gate drive voltage (the supply volt-
age to the ADP3412) dictates whether standard threshold or
logic-level threshold MOSFETs must be used. Since V
GATE
< 8 V,
logic-level threshold MOSFETs (V
GS(TH)
< 2.5 V) are strongly
recommended.
The maximum output current I
O
determines the R
DS(ON)
require-
ment for the power MOSFETs. When the ADP3160 is operating
in continuous mode, the simplifying assumption can be made
that in each phase one of the two MOSFETs is always conduct-
ing the average inductor current. For V
IN
= 12 V and
V
OUT
= 1.6 V, the duty ratio of the high-side MOSFET is:
V
V
IN
The duty ratio of the low-side (synchronous rectifier) MOSFET is:
=
1
86. %
–
The maximum rms current of the high-side MOSFET during
normal operation is:
D
HSF
OUT
=
=
13 3%
(11)
D
D
LSF
HSF
=
(12)
I
I
D
I
I
A
HSF MAX
(
O
2
HSF
L RIPPLE
(
￥
3
O
)
)
.
=
￥
+
ê
ˉ=
1
9 8
2
2
(13)
The maximum rms current of the low-side MOSFET during
normal operation is:
I
I
D
D
A
LSF MAX
(
HSF MAX
(
LSF
HSF
)
)
=
=
25
(14)
The R
DS(ON)
for each MOSFET can be derived from the allowable
dissipation. If 10% of the maximum output power is allowed for
MOSFET dissipation, the total dissipation in the four MOSFETs
of the 2-phase converter will be:
=
=
0 1 1 57
Allocating half of the total dissipation for the pair of high-side
MOSFETs and half for the pair of low-side MOSFETs, and
assuming that the resistive and switching losses of the high-side
MOSFET are equal, the required maximum MOSFET resis-
tances will be:
P
P
V
I
V
A
W
MOSFET TOTAL
MIN
.
O
53 4
MOSFET TOTAL
(
)
(
)
.
.
.
.
￥
￥
￥
=
0 1
8 4
(15)
R
P
8
I
.
R
W
A
m
DS ON HS MAX
(
)
MOSFET TOTAL
￥
8 4
8
HSF(
DS ON HS MAX
(
)
(
)
(
)
)
(
)
9 8
)
=
=
￥
=
W
11
2
2
(16)
R
P
4
I
R
W
A
m
DS ON LS MAX
(
)
MOSFET TOTAL
￥
8 4
4
25
LSF(
DS ON LS MAX
(
)
(
)
(
)
)
.
(
)
.
(
)
=
=
￥
=
W
3 4
2
2
(17)
Note that there is a trade-off between converter efficiency and
cost. Larger MOSFETs reduce the conduction losses and allow
higher efficiency, but increase the system cost. If efficiency is
not a major concern, a Fairchild FDB7030L (R
DS(ON)
= 7 m
W
nominal, 10 m
W
worst case) for the high-side and a Fairchild
FDB8030L (R
DS(ON)
= 3.1 m
W
nominal, 5.6 m
W
worst case)
for the low-side are good choices. The high-side MOSFET
dissipation is:
(
￥
￥
2
where the second term represents the turn-off loss of the
MOSFET and the third term represents the turn-on loss due to
the stored charge in the body diode of the low-side MOSFET.
(In the second term,
Q
G
is the gate charge to be removed from
the gate for turn-off and
I
G
is the gate turn-off current. From
P
R
I
V
I
Q
f
I
V
(
Q
f
HSF
DS ON HS
￥
)
HFS MAX
(
IN
L PK
(
G
SW
G
IN
RR
SW
=
￥
)
+
￥
+
￥
￥
)
(
)
)
2
(18)
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