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參數資料
| 型號： | AD8361-EVAL |
| 廠商： | Analog Devices, Inc. |
| 英文描述： | LF to 2.5 GHz TruPwr⑩ Detector |
| 中文描述： | 低頻至2.5 GHz TruPwr⑩探測器 |
| 文件頁數： | 9/16頁 |
| 文件大小： | 306K |
| 代理商： | AD8361-EVAL |
AD8361
–9–
REV. A
CIRCUIT DESCRIPTION
The AD8361 is an rms-responding (mean power) detector pro-
viding an approach to the exact measurement of RF power that
is basically independent of waveform. It achieves this function
through the use of a proprietary technique in which the outputs
of two identical squaring cells are balanced by the action of a
high-gain error ampli
fi
er.
The signal to be measured is applied to the input of the
fi
rst
squaring cell, which presents a nominal (LF) resistance of 225
between the pin RFIN and COMM (connected to the ground
plane). Since the input pin is at a bias voltage of about 0.8 V
above ground, a coupling capacitor is required. By making this
an external component, the measurement range may be extended
to arbitrarily low frequencies.
The AD8361 responds to the voltage, V
IN
, at its input, by squaring
this voltage to generate a current proportional to V
IN
squared.
This is applied to an internal load resistor, across which is con-
nected a capacitor. These form a low-pass
fi
lter, which extracts
the mean of V
IN
squared. Although essentially voltage-responding,
the associated input impedance calibrates this port in terms of
equivalent power. Thus 1 mW corresponds to a voltage input of
447 mV rms. In the Application section it is shown how to match
this input to 50
.
The voltage across the low-pass
fi
lter, whose frequency may
be arbitrarily low, is applied to one input of an error-sensing
ampli
fi
er. A second identical voltage-squaring cell is used to
close a negative feedback loop around this error ampli
fi
er.
This second cell is driven by a fraction of the quasi-dc output
voltage of the AD8361. When the voltage at the input of the
second squaring cell is equal to the rms value of V
IN
, the loop
is in a stable state, and the output then represents the rms value of
the input. The feedback ratio is nominally 0.133, making the
rms-dc conversion gain
×
7.5, that is
V
OUT
= 7.5
×
V
IN
rms
By completing the feedback path through a second squaring cell,
identical to the one receiving the signal to be measured, several
bene
fi
ts arise. First, scaling effects in these cells cancel; thus, the
overall calibration may be accurate, even though the open-loop
response of the squaring cells taken separately need not be.
Note that in implementing rms-dc conversion, no reference
voltage enters into the closed-loop scaling. Second, the tracking
in the responses of the dual cells remains very close over tempera-
ture, leading to excellent stability of calibration.
The squaring cells have very wide bandwidth with an intrinsic
response from dc to microwave. However, the dynamic range
of such a system is fairly small, due in part to the much larger
dynamic range at the output of the squaring cells. There are
practical limitations to the accuracy with which very small error
signals can be sensed at the bottom end of the dynamic range,
arising from small random offsets; these set the limit to the
attainable accuracy at small inputs.
On the other hand, the squaring cells in the AD8361 have
a
“
Class-AB
”
aspect; the peak input is not limited by their
quiescent bias condition, but is determined mainly by the
eventual loss of square-law conformance. Consequently, the top
end of their response range occurs at a fairly large input level
(about 700 mV rms) while preserving a reasonably accurate
square-law response. The maximum usable range is, in practice,
limited by the output swing. The rail-to-rail output stage can
swing from a few millivolts above ground to less than 100 mV
below the supply. An example of the output induced limit: given
a gain of 7.5 and assuming a maximum output of 2.9 V with a 3 V
supply; the maximum input is (2.9 V rms)/7.5 or 390 mV rms.
Filtering
An important aspect of rms-dc conversion is the need for
averaging (the function is
root-MEAN-square
). For complex RF
waveforms such as occur in CDMA, the
fi
ltering provided by
the on-chip low-pass
fi
lter, while satisfactory for CW signals above
100 MHz, will be inadequate when the signal has modulation
components that extend down into the kilohertz region. For this
reason, the FLTR pin is provided: a capacitor attached between
this pin and VPOS can extend the averaging time to very low
frequencies.
Offset
An offset voltage can be added to the output (when using the
micro_SOIC version) to allow the use of A/D converters whose
range does not extend down to ground. However, accuracy at
the low end will be degraded because of the inherent error in this
added voltage. This requires that the pin IREF (
internal reference
)
should be tied to VPOS and SREF (
supply reference
) to ground.
In the IREF mode, the intercept is generated by an internal
reference cell, and is a
fi
xed 350 mV, independent of the supply
voltage. To enable this intercept, IREF should be open-circuited,
and SREF should be grounded.
In the SREF mode, the voltage is provided by the supply. To
implement this mode, tie IREF to VPOS and SREF to VPOS. The
offset is then proportional to the supply voltage, and is 400 mV
for a 3 V supply and 667 mV for a 5 V supply.
USING THE AD8361
Basic Connections
Figures 32, 33, and 34 show the basic connections for the
micro_SOIC version AD8361 in its three operating modes. In all
modes, the device is powered by a single supply of between 2.7V
and 5.5 V. The VPOS pin is decoupled using 100 pF and 0.01
μ
F
capacitors. The quiescent current of 1.1 mA in operating mode
can be reduced to 1
μ
A by pulling the PWDN pin up to VPOS.
A 75
external shunt resistance combines with the ac-coupled
input to give an overall broadband input impedance near 50
.
Note that the coupling capacitor must be placed between the in-
put and the shunt impedance. Input impedance and input coupling
are discussed in more detail below.
The input coupling capacitor combines with the internal input
resistance (Figure 13) to give a high-pass corner frequency
given by the equation
f
C
R
dB
C
IN
3
1
2
=
×
×
π
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PDF描述 |
|---|---|
| AD8362 | 50 Hz to 2.7 GHz 60 dB TruPwr⑩ Detector |
| AD8362-EVAL | 50 Hz to 2.7 GHz 60 dB TruPwr⑩ Detector |
| AD8362ARU | 50 Hz to 2.7 GHz 60 dB TruPwr⑩ Detector |
| AD8362ARU-REEL7 | 50 Hz to 2.7 GHz 60 dB TruPwr⑩ Detector |
| AD8362ARUZ-REEL71 | 50 Hz to 2.7 GHz 60 dB TruPwr⑩ Detector |
相關代理商/技術參數 |
參數描述 |
|---|---|
| AD8361-EVALZ | 制造商:Analog Devices 功能描述:LF TO 2.5 GHZ TRUPWR DETECTOR - Bulk |
| AD8362 | 制造商:AD 制造商全稱:Analog Devices 功能描述:50 Hz to 2.7 GHz 60 dB TruPwr⑩ Detector |
| AD8362_1 | 制造商:AD 制造商全稱:Analog Devices 功能描述:50 Hz to 3.8 GHz 65 dB TruPwr? Detector |
| AD8362ARU | 功能描述:IC PWR DETECTOR 3.8GHZ 16-TSSOP RoHS:否 類別:RF/IF 和 RFID >> RF 檢測器 系列:- 產品變化通告:Product Discontinuation 15/May/2006 標準包裝:3,000 系列:- 頻率:100MHz ~ 2GHz RF 型:手機，GSM，DCS，PCS 輸入范圍:- 精確度:- 電源電壓:2.7 V ~ 5.5 V 電流 - 電源:300µA 包裝:帶卷 (TR) 封裝/外殼:SC-74，SOT-457 其它名稱:NCS5000SNT1GOS |
| AD8362ARU-REEL | 制造商:AD 制造商全稱:Analog Devices 功能描述:50 Hz to 3.8 GHz 65 dB TruPwr? Detector |
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